Method and System for Using a Wireless Local Area Network (WLAN) Phase Shifter for Smart Antenna Beam Steering

ABSTRACT

Aspects of a method and system for using a wireless local area network (WLAN) phase shifter for smart antenna beam steering are presented. Aspects of the system may enable determination of an angle of arrival (AOA) for signals received at a receiving station in a wireless network. Based on the AOA value, the receiving station may enable orientation of antenna in a smart antenna system. In a switched beam smart antenna system, antenna element(s) may be selected, which are most closely oriented toward the AOA. In an adaptive array smart antenna system, antenna beam may be steered, or reoriented, based on the AOA.

CROSS-REFERENCE TO RELATED APPLICATIONS/INCORPORATION BY REFERENCE

Not Applicable.

FIELD OF THE INVENTION

Certain embodiments of the invention relate to data communication. More specifically, certain embodiments of the invention relate to a method and system for using a wireless local area network (WLAN) phase shifter for smart antenna beam steering.

BACKGROUND OF THE INVENTION

Wireless local area network (WLAN) systems enable the communication of data via a wireless communication medium by, for example, transmitting radio frequency (RF) signals that carry data between a transmitting station and a receiving station. A range of frequencies, referred to as the WLAN frequency spectrum, may be utilized for communication between stations in a WLAN system. The frequency spectrum may be divided into RF channels wherein each RF channel represented an assigned frequency within the WLAN frequency spectrum. Each RF channel may, in turn, comprise a range of frequencies referred to as an RF channel bandwidth. Each RF channel within the WLAN frequency spectrum may comprise a range of frequencies, which is non-overlapping and distinct from other RF channels.

Smart antenna systems may be utilized in WLAN systems to enable the transmission and/or reception of signals via a wireless communication medium. A smart antenna system may refer to a system, which may dynamically configure its directivity pattern. For a smart antenna system located at a transmitting station, most of the signal energy may be radiated in a particular direction. The desired transmission directivity pattern may be configured at a transmitting station based on the location of the receiving station. For example, the desired transmission directivity pattern may be selected to maximize the amount of signal energy transmitted by the transmitting station, which is received at the receiving station.

For a smart antenna system located at a receiving station, an antenna directivity pattern may be configured to coincide with the angle of arrival (AOA) of the received signals.

Antenna directionality is expressed in dBi (Decibel Isotropic) which is a measurement of focus that an antenna has compared to a mathematically ideal isotropic antenna which has a uniform focus in all directions.

Smart antenna systems may contain a plurality of highly directional antenna elements, wherein each antenna element may be oriented in a particular direction. In such highly directional antenna systems, the smart antenna system may enable selection of antenna elements to achieve a desired transmission directivity pattern. Such systems may be referred to as switched beam smart antenna systems. Smart antenna systems may also contain a plurality of omnidirectional antenna elements, wherein the antenna directivity pattern may be oriented, or steered, in various directions by adjusting the phase of the signal applied to each antenna element. Such systems may be referred to as adaptive array smart antenna systems.

Antenna directivity pattern in a smart antenna system may be selected based on received signal strength indication (RSSI) measurements taken from received signals and/or by analyzing the rate at which acknowledgments from previously transmitted protocol data units (PDU) are received. The acknowledgments may provide an indication to the transmitting station that previously transmitted PDUs were successfully received by the receiving station.

Further limitations and disadvantages of conventional and traditional approaches will become apparent to one of skill in the art, through comparison of such systems with some aspects of the present invention as set forth in the remainder of the present application with reference to the drawings.

BRIEF SUMMARY OF THE INVENTION

A method and system for using a wireless local area network (WLAN) phase shifter for smart antenna beam steering, substantially as shown in and/or described in connection with at least one of the figures, as set forth more completely in the claims.

These and other advantages, aspects and novel features of the present invention, as well as details of an illustrated embodiment thereof, will be more fully understood from the following description and drawings.

BRIEF DESCRIPTION OF SEVERAL VIEWS OF THE DRAWINGS

FIG. 1 is an exemplary wireless communication system, in accordance with an embodiment of the invention.

FIG. 2 is an exemplary transceiver comprising a smart antenna system, in accordance with an embodiment of the invention.

FIG. 3 is an illustration exemplary transmitted data unit in a WLAN, which may be utilized in connection with an embodiment of the invention.

FIG. 4A is an exemplary diagram showing a WLAN phase shifter for smart beam steering, in accordance with an embodiment of the invention.

FIG. 4B is another exemplary diagram showing a WLAN phase shifter for smart beam steering, in accordance with an embodiment of the invention.

FIG. 5 is an exemplary diagram showing a WLAN phase shifter for smart beam steering utilizing directional antennas, in accordance with an embodiment of the invention.

FIG. 6 is a flowchart illustrating exemplary steps for WLAN phase shifter for smart beam steering utilizing omnidirectional antennas, in accordance with an embodiment of the invention.

FIG. 7 is a flowchart illustrating exemplary steps for WLAN phase shifter for smart beam steering utilizing directional antennas, in accordance with an embodiment of the invention.

DETAILED DESCRIPTION OF THE INVENTION

Certain embodiments of the invention may be found in a method and system for using a wireless local area network (WLAN) phase shifter for smart antenna beam steering. Various embodiments of the invention comprise a system, which enables selection and/or adaptive steering of antenna directivity pattern in a smart antenna system. For a smart antenna system, which is located at a receiving station, the antenna directivity may be selected based on the angle of arrival (AOA) of a received signal. In a switched beam smart antenna system, antenna element(s) may be selected, which are most closely oriented toward the AOA. In an adaptive array smart antenna system, antenna directivity pattern may be steered, or reoriented, based on the AOA.

FIG. 1 is an exemplary wireless communication system, in accordance with an embodiment of the invention. Referring to FIG. 1, there is shown an access point (AP) 102, a wireless local area network (WLAN) station (STA) 104, and a STA 106. As shown in FIG. 1, the AP 102 comprises a plurality of omnidirectional antennas 112 a and 112 b and a smart antenna system 122. The antennas 112 a and 112 b may be separated by a distance, d. Each of the omnidirectional antennas 112 a and 112 b may be capable of receiving signals across a 360° range of AOA values with equal gain. In various embodiments of the invention, the smart antenna system 122 may be positioned at an intermediate location in relation to the antennas 112 a and 112 b. In various embodiments of the invention, the smart antenna system may comprise a switched beam smart antenna system and/or an adaptive array smart antenna system. The STA 104 comprises an antenna 114, and the STA 106 comprises an antenna 116. The AP 102 and the STA 104 may communicate wirelessly via a radio frequency (RF) channel 134. The AP 102 and STA 106 may communicate wirelessly via an RF channel 136. The antennas 112 a and 112 b and the smart antenna system 122 may enable the AP 102 to transmit and/or receive signals. The antenna 114 may enable the STA 104 to transmit and/or receive signals. The antenna 116 may enable the STA 106 to transmit and/or receive signals. The AP 102, STA 104 and STA 106 may enable communication based on one or more IEEE 802 standards, for example IEEE 802.11.

In operation, the STA 104 may transmit signals to the AP 102 via the RF channel 134 and the STA 106 may transmit signals to the AP 102 via the RF channel 136. The AOA value for signals received at the AP 102 via the RF channel 134 may be represented AOA=α₁. The AOA value for signals received at the AP 102 via the RF channel 136 may be represented AOA=α₂. The AOA values may be measured relative to a plane of incidence 132. The AP 102 may receive signals via the antenna 112 a, 112 b and/or the smart antenna system 122. In various embodiments of the invention, the AP 102 may enable reception of signals via RF channels 134 and/or 136 by adaptively steering the smart antenna system 122. For example, the AP 102 may adaptively steer antenna to an angle of α₁ when receiving signals via the RF channel 134. The AP 102 may adaptively steer antenna to an angle of α₂ when receiving signals via the RF channel 136.

Depending upon the relative positions of the AP 102 and the STA 104, the length of the signal path, d₁, from the transmitting antenna 114 to the receiving antenna 112 a may differ from the length of the corresponding signal path, d₂, from the transmitting antenna 114 to the receiving antenna 112 b. When d₁≠d₂ there may be a relative phase shift between the signal received at antenna 112 a and the signal received at receiving antenna 112 b.

During an exemplary signal location process, the AP 102 may select the antenna 112 a to receive one or more signals. The AP 102 may then select the antenna 112 b to receive subsequent one or more signals. The AP 102 may perform a signal correlation computation between signals received via the antenna 112 a and corresponding signals received via the antenna 112 b to determine the relative phase shift value. In various embodiments of the invention, the AP 102 may utilize a relative phase shift value to adaptively steer smart antenna 122.

FIG. 1 shows a smart antenna system 122, which can be a switched beam or adaptive array system. For example, an exemplary embodiment of the invention may comprise four (4) antenna elements in either a switched beam smart antenna or an adaptive array smart antenna system. In an exemplary switched beam smart antenna system, the antenna elements may be configured in a sector pattern. For example, in an exemplary sector pattern each of the antenna elements may be oriented within a distinct 90° range of potential AOA values (e.g. 0° to 89°, 90° to 179°, 180° to 269° and 270° to 359°). In an exemplary adaptive array smart antenna system, each of the antenna elements may be configured in a sector pattern, in which each antenna element may be individually steered to sweep across the range of AOA values within each respective sector (e.g. 0° to 89°, 90° to 179°, 180° to 269° and 270° to 359°, respectively).

FIG. 2 is an exemplary transceiver comprising a smart antenna system, which may be utilized in connection with an embodiment of the invention. Referring to FIG. 2, there is shown a transceiver system 200 and a smart antenna system 220. The transceiver system 200 may comprise at least a receiver 202, a transmitter 204, a processor 206, and a memory 208. Although a transceiver is shown in FIG. 2, transmit and receive functions may be separately implemented.

The processor 206 may enable digital receiver and/or transmitter functions in accordance with applicable communications standards. The processor 206 may also perform various processing tasks on received data. The processing tasks may comprise computing channel estimates, which may characterize the wireless communication medium, delineating packet boundaries in received data, and computing packet error rate statistics indicative of the presence or absence of detected bit errors in received packets.

The receiver 202 may perform receiver functions that may comprise, but are not limited to, the amplification of received RF signals, generation of frequency carrier signals corresponding to selected RF channels, for example uplink channels, the down-conversion of the amplified RF signals by the generated frequency carrier signals, demodulation of data contained in data symbols based on application of a selected demodulation type, and detection of data contained in the demodulated signals. The RF signals may be received via antenna 220. The transmit and receive (T/R) switch 232 may be configured to enable antenna 220 to be utilized for reception of signals. The data received via the signals may be communicated to the processor 206.

The transmitter 204 may perform transmitter functions that may comprise, but are not limited to, modulation of received data to generated data symbols based on application of a selected modulation type, generation of frequency carrier signals corresponding to selected RF channels, for example downlink channels, the up-conversion of the data symbols by the generated frequency carrier signals, and the generation and amplification of RF signals. The data may be received from the processor 206. The RF signals may be transmitted via antenna 220. T/R switch 232 may be configured to enable antenna 220 to be utilized for transmission of signals.

The memory 208 may comprise suitable logic, circuitry and/or code that may enable storage and/or retrieval of data and/or code. The memory 208 may utilize any of a plurality of storage medium technologies, such as volatile memory, for example random access memory (RAM), and/or non-volatile memory, for example electrically erasable programmable read only memory (EEPROM).

In the context of the present application, the processor 206 and the memory 208 may enable the reception of signals via a wireless communication medium by adjusting directivity pattern of antenna 220. The processor 206 and the memory 208 may enable the selection of antennas 112 a and/or 112 b to receive signals. Based on the received signals, the processor 206 and the memory 208 may enable the computation of the relative phase shift of the signals received by antennas 112 a and 112 b. The processor 206 and the memory 208 may enable the selection of the candidate AOA value, whereby antenna 220 may be adaptively steered. The adaptively steered antenna 220 may be reoriented to point in the direction corresponding to the selected AOA value to enable the reception of subsequent signals. In a switched beam smart antenna system, the processor 206 and the memory 208 may select antenna elements based on the orientation of the antenna elements relative to the selected AOA value. In an adaptive array smart antenna system, the processor 206 and the memory 208 may reorient antenna 220 based on the determined AOA value

FIG. 3 is an illustration exemplary transmitted data unit in a WLAN, which may be utilized in connection with an embodiment of the invention. Referring to FIG. 3, there is shown a physical layer protocol data unit (PPDU) 300. The PPDU 300 is exemplary of a PPDU, which may be transmitted, via a wireless communication medium, in a WLAN system. The PPDU 300 may comprise a short training sequence and a long training sequence. The short training sequence may comprise ten short training symbols 302 a, 302 b, 302 c, 302 d, 302 e, 302 f, 302 g, 302 h, 302 i and 302 j. The long training sequence may comprise two long training symbols 306 a and 306 b. Each of the short training symbols may represent a predetermined data symbol value, which is transmitted for a predetermined time duration, for example, 0.8 μs. Consequently, in the exemplary illustration of FIG. 3, the duration of the short training sequence is 8 μs

Following the completion of the short training sequence, the long training sequence may begin. In the exemplary PPDU 300, the long training sequence begins with transmission of a long training sequence guard interval (GI2) 304. The GI2 304 represents a time duration, which begins at the end of transmission of the last short training symbol 302 j and ends with the beginning of transmission of the first long training symbol 306 a. In the exemplary PPDU 300, the GI2 304 time duration is 1.6 μs. Each of the long training symbols may represent a predetermined data symbol value, which is transmitted for a predetermined time duration, for example, 3.2 μs. Consequently, in the exemplary illustration of FIG. 3, the duration of the long training sequence, which comprises the GI2 304 and two long training symbols 306 a and 306 b, is 8 μs. The short training symbols 302 a, 302 b, 302 c, 302 d, 302 e, 302 f, 302 g, 302 h, 320 i and 302 j, and the long training symbols 306 a and 306 b may form the preamble field within the PPDU 300.

Following the completion of the long training sequence, the signal segment in the PPDU 300 may be transmitted. The signal segment may comprise a guard interval 308 and a signal symbol 310. The GI 308 represents a time duration, which begins at the end of transmission of the last long training symbol 306 b and ends with the beginning of transmission of the signal symbol 310. In the exemplary PPDU 300, the GI 308 time duration is 0.8 μs. The signal symbol 310 may comprise data, which indicates the data transfer rate (as measured in megabits per second Mb/s, for example) supported by the PPDU 300 and the quantity of data being transferred in the data payload portion of the PPDU 300 (as measured in octets, for example). The signal symbol may be transmitted for a predetermined time duration, for example, 3.2 μs.

Following the completion of the signal segment, the data payload in the PPDU 300 may be transmitted. The data payload may comprise a plurality of data symbols 314 a . . . 314 n, each separated by a GI 312 a . . . 312 n. Each data symbol 314 a . . . 314 n may comprise data, which is being transmitted from an AP 102 to a STA 104, for example. Each data symbol 314 a . . . 314 n may be transmitted for a predetermined time duration, for example, 3.2 μs. The number of bits transmitted in each data symbol may be determined based on the contents of the signal symbol 310. For example, the data rate supported by the PPDU 300 may be computed based on the number of bits transmitted in each data symbol 314 a, b _(sym), divided by the data symbol duration 3.2 μs. The aggregate number of bits transmitted in the plurality of data symbols 314 a . . . 314 n may also be determined based on the contents of the signal symbol 310.

In operation, a STA 104 may transmit a PPDU 300 by transmitting a plurality of signals at distinct time instants, t, via the antenna 114. Each signal may comprise a symbol from the PPDU 300. For example, the STA 104 may transmit a signal when transmitting the short training symbol 302 a and may transmit a subsequent signal when transmitting the short training symbol 302 b. The signals transmitted by the STA 104 at distinct time instants, t, may be represented as signals s₁(t). The signals received by the AP 102 at distinct time instants, t, may be represented as signals r₁(t). The STA 106 may transmit a PPDU 300 by transmitting a plurality of signals via the antenna 116. Each signal may comprise a symbol from the PPDU 300. The signals transmitted by the STA 106 may be represented as signals s₂(t). The signals received by the AP 102 at distinct time instants, t, may be represented as signals r₂(t).

FIG. 4A is an exemplary diagram showing a WLAN phase shifter for smart beam steering, in accordance with an embodiment of the invention. Referring to FIG. 4A, the STA 104 may transmit signals s (t), which may be represented as shown in the following equation:

s(t)=Re{A(t)·e ^(j·ω) ^(t) ^(·t)}

where ω_(t) refers to the carrier frequency generated by STA 104, t represents time, A(t) represents the baseband signal transmitted by the STA 104, and j represents √{square root over (−1)}.

Given the signal s(t) as shown in equation [1], a line of sight (LOS) signal represented by the signal path 402 b and received at the AP 102 via receiving antenna 112 a, r _(112a)(t), may be represented as shown in the following equation:

$\begin{matrix} {{r_{112\; a}(t)} \approx {{{h_{112\; a} \cdot R}\; e\left\{ {{A(t)} \cdot ^{j \cdot {\lbrack{\omega_{t} \cdot {({t + \frac{d_{402\; b}}{C}})}}\rbrack}}} \right\}} + \eta_{112\; a}}} & \lbrack 2\rbrack \end{matrix}$

where h_(112a) refers to the attenuation of the signal along signal path 402 b, d _(402b) refers to the length of the signal path 402 b, C refers to the velocity of propagation of RF signal via RF channel 134 and η_(112a) refers to the thermal noise generated by antenna 112 a.

The LOS signal received at the AP 102 via receiving antenna 112 b, r _(112b)(t), may be represented as shown in the following equation:

$\begin{matrix} {{r_{112\; b}(t)} \approx {{{h_{112\; b} \cdot R}\; e\left\{ {{A(t)} \cdot ^{j \cdot {\lbrack{\omega_{t} \cdot {({t + \frac{d_{402\; c}}{C}})}}\rbrack}}} \right\}} + \eta_{112\; b}}} & \lbrack 3\rbrack \end{matrix}$

where h_(112b) refers to the attenuation of the signal along signal path 402 c, d _(402c) refers to the length of the signal path 402 c, C refers to the velocity of propagation of RF signal via RF channel 134 and η_(112b) refers to the thermal noise generated by antenna 112 b.

A relative phase shift, θ, which refers to the phase of the LOS signal received at receiving antenna 112 b relative to the phase of the LOS signal received at the receiving antenna 112 a may be represented as shown in the following equation:

$\begin{matrix} {\theta = {\frac{\omega_{t}}{C}\left( {d_{402\; c} - d_{402\; b}} \right)}} & \lbrack 4\rbrack \end{matrix}$

Referring to FIG. 4A, the signal path 402 b represents the signal path for the signal s(t), transmitted from antenna 114 to received signal r_(112a)(t) at antenna 112 a. The signal path 402 b length is represented as d_(402b). The signal path 402 c represents the signal path for the signal s(t), transmitted from antenna 114 to received signal r_(112b)(t) at antenna 112 b. The signal path 402 c length is represented as d_(402c). A reference path 402 a represents the distance from the antenna 114 to a midpoint 404, which is midway between the antennas 112 a and 112 b located along the plane of incidence 132. The midpoint 404 may correspond to the location of the smart antenna system 122. A midpoint distance, representing the distance from the midpoint 404 to the antenna 112 a may be represented as ½d, where d represents the distance between the antenna 112 a and the antenna 112 b. The midpoint distance may also represent the distance from the midpoint 404 to the antenna 112 b (½d). The length of the reference path 402 a is represented as R. The AOA for signals received from the STA 104 at the AP 102 may be represented by the angle at which the reference path 402 a intersects the plane of incidence 132. As shown in FIG. 4A, the AOA value may be represented as AOA=α. The AOA value AOA=α may represent the angle of arrival for signals received at the smart antenna system 122.

Based on the AOA value, AOA=α, the antenna distance, d, the midpoint distance, ½d, and the reference path 402 a length, R, the signal path 402 b length, d₂, and the signal path 402 c length, d₁, may be represented as shown in the following equations:

$\begin{matrix} {d_{402\; b}^{2} = {R^{2} + \frac{d^{2}}{4} - {R \cdot d \cdot {\cos (\alpha)}}}} & \lbrack 5\rbrack \end{matrix}$

and:

$\begin{matrix} {d_{402\; c}^{2} = {R^{2} + \frac{d^{2}}{4} + {R \cdot d \cdot {\cos (\alpha)}}}} & \lbrack 6\rbrack \end{matrix}$

Based on equations [4], [5] and [6], the following equation may be derived:

$\begin{matrix} {{\frac{\theta}{\omega_{t}} \cdot C \cdot \left( {d_{402\; c} + d_{402\; b}} \right)} = {2 \cdot R \cdot d \cdot {\cos (\alpha)}}} & \lbrack 7\rbrack \end{matrix}$

For values R>>d, equation [7] may be approximated as shown in the following equation:

$\begin{matrix} {{\cos (\alpha)} \cong {\frac{C}{\omega_{t} \cdot d} \cdot \theta}} & \lbrack 8\rbrack \end{matrix}$

Based on the relationship:

cos(α)=cos(−α)  [9]

Two candidates AOA values may be computed as follows:

$\begin{matrix} {\alpha_{1} \in \left\{ {{{arc}\; {\cos \left( {\frac{C}{\omega_{t} \cdot d} \cdot \theta} \right)}},{{- {arc}}\; {\cos \left( {\frac{C}{\omega_{t} \cdot d} \cdot \theta} \right)}}} \right\}} & \lbrack 10\rbrack \end{matrix}$

In operation, in an exemplary embodiment of the invention, a STA 104 may transmit a PPDU 300 via the transmitting antenna 114. The AP 102 may be initially configured to receive signals via the receiving antenna 112 a. These signals may be represented as signals r_(112a)(t) as shown in equation [2], for example. The AP 102 receiver 202 converts RF signal r_(112a)(t) into baseband signal b_(112a)(t):

$\begin{matrix} {{b_{112\; a}(t)} = {{g \cdot {r_{112\; a}(t)} \cdot ^{j{\lbrack{{{- \omega_{t}} \cdot t} + \phi}\rbrack}}} \approx {{g \cdot h_{112\; a} \cdot {A(t)} \cdot ^{j{\lbrack{{({\omega_{t} - \omega_{r}})} \cdot {({t + \frac{d_{1}}{C}})}}\rbrack}}} + {g \cdot \psi \cdot \eta_{112\; a}}}}} & \lbrack 11\rbrack \end{matrix}$

where ω_(r) refers to the local oscillator frequency generated by AP 102, φ refers to the phase difference between the oscillator used to generate the transmitted signal at the STA 104 and the oscillator used to down convert received signal at the AP 102, g refers to the gain of the receiver and ψ refers to the noise figure of the receiver.

The AP 102 may detect a received signal upon receipt of the short training symbol 302 a. The AP 102 may receive short training symbols 302 b and 302 c via the receiving antenna 112 a. The AP 102 may utilize the received short training symbols 302 b and 302 c to compute the frequency difference, ω_(e):

$\begin{matrix} {\omega_{e} = {{{{- \frac{1}{T}} \cdot {arc}}\; {\tan \left( {\int_{t = t_{1}}^{t_{1} + T}{{{b_{112\; a}(t)} \cdot {b_{112\; a}^{*}\left( {t + T} \right)}}\ {t}}} \right)}} \approx {\omega_{t} - \omega_{r}}}} & \lbrack 12\rbrack \end{matrix}$

where t₁ represents the time of the beginning of the short training symbol 302 b, T refers to the symbol interval of the short training symbol 302 b, T=0.8 us, (arg)* represents complex conjugate operation on the argument (for example, arg=b_(112a) in equation [12]). The value ω_(e) may represent the clock frequency offset between the transmitter, STA 104, and the receiver, AP 102. In addition, the AP 102 may determine the power of the received baseband signal, b_(112a)(t):

$\begin{matrix} {P_{112\; a} = {\frac{1}{2\; T}{\int_{t = t_{1}}^{t_{1} + {2T}}{{{b_{112\; a}(t)}}^{2}\ {t}}}}} & \lbrack 13\rbrack \end{matrix}$

After receiving short training symbols 302 b and 302 c, via receiving antenna 112 a, the AP 102 may be configured to receive subsequent signals via the receiving antenna 112 b. These signals may be represented as signals r_(112b)(t) as shown in equation [3], for example. The AP 102 receiver 202 down converts RF signal r_(112b)(t) into baseband signal b_(112b)(t):

$\begin{matrix} {{b_{112\; b}(t)} = {{g \cdot {r_{112\; b}(t)} \cdot ^{j{\lbrack{{{- \omega_{t}} \cdot t} + \phi}\rbrack}}} \approx {{g \cdot h_{112\; b} \cdot {A(t)} \cdot ^{j{\lbrack{{({\omega_{t} - \omega_{r}})} \cdot {({t + \frac{d_{2}}{C}})}}\rbrack}}} + {g \cdot \psi \cdot \eta_{112\; b}}}}} & \lbrack 14\rbrack \end{matrix}$

The AP 102 may receive short training symbols 302 e and 302 f via the receiving antenna 112 b. The AP 102 may also compute the relative phase of the signals b_(112a)(t) and b_(112b)(t) to determine a relative phase, θ by correlating baseband signal corresponding to short training symbols 302 b and 302 c received via antenna 112 a and short training symbols 302 e and 302 f received via antenna 112 b:

$\begin{matrix} {\theta \approx {{{- {arc}}\; {\tan \left( {\int_{t = t_{1}}^{t_{1} + {2T}}{{{b_{1}(t)} \cdot {b_{2}^{*}\left( {t + {3T}} \right)}}{t}}} \right)}} + {3T\; \omega_{e}}}} & \lbrack 15\rbrack \end{matrix}$

where ω_(e) refers to the frequency difference computed as shown in equation [12]. In addition, the AP 102 may determine the power of the received baseband signal b_(112b)(t):

$\begin{matrix} {P_{112\; b} = {\frac{1}{2T}{\int_{t = {t_{1} + {3T}}}^{t_{1} + {5T}}{{{b_{112\; a}(t)}}^{2}\ {t}}}}} & \lbrack 16\rbrack \end{matrix}$

In various embodiments of the invention, during the signal location process, a set of candidate AOA values can be determined based on relative phase shift value θ according to equation [10].

The AP 102 may maintain a discrete set of relative phase shift values θ_(i),iε[0;N] and corresponding sets of candidate AOA values{α_(i),−α_(i)}. After calculating the value of θ the AP 102 may round it to the nearest θ_(i) and adaptively steer smart antenna 122 in the direction of one of the two AOA candidates {α_(i),−α_(i)} and proceed with the reception of the remainder of PPDU 300 using smart antenna 122. The AP 102 maintains a discrete set of antenna indication values ant_ind_(i) corresponding to the set of relative phase shift values θ_(i),iε[0;N]. The selection between α_(i) and −α_(i) AOA candidates is based on antenna indication value ant_ind_(i). When ant_ind_(i)=0 the smart antenna 122 is steered in the direction of α_(i). When ant_ind_(i)=1 the smart antenna 122 is steered in the direction of −α_(i). If AP 102 receives PPDU 300 without errors the value remains unchanged otherwise antenna indication value is changed to the opposite.

FIG. 4B is another exemplary diagram showing a WLAN phase shifter for smart antenna beam steering, in accordance with an embodiment of the invention. FIG. 4B presents a variation of the system shown in FIG. 4A, wherein the STA 104 is located such that the AOA value at the plane of incidence 132 is represented AOA=−α. In this instance, AP 102 may compute candidate AOA values AOA=α and AOA=−α, substantially as shown for the system in FIG. 4A. For the very first PPDU received by AP 102 from STA 104 the ant_ind_(i) may be set to 0 and the smart antenna 122 may be steered in the direction of AOA=α_(i) away from the STA 104. But once PPDU reception fails the value of ant_ind_(i) will be changed to 1 and the smart antenna 122 will be steered in the correct direction of AOA=−α_(i) for reception of subsequent PPDUs from STA 104.

FIG. 5 is an exemplary diagram showing a WLAN phase shifter for smart beam steering utilizing directional antennas, in accordance with an embodiment of the invention. FIG. 5 presents a variation of the system shown in FIG. 4A, wherein the omnidiretional antennas 122 a and 122 b may be replaced by directional antennas 512 a and 512 b, for example log-periodic antennas. The directional antenna may be capable of receiving signals across a range of AOA values (which is less than 360°) with substantially equal gain. Received signals for which the AOA value is outside of the AOA value range for the directional antenna may be received with lower gain than for received signals for which the AOA value is within the AOA value range. An exemplary directional antenna may, for example, have a 180° AOA value range. In various embodiments of the invention, the antenna 512 b may be oriented at a 180° position relative to the antenna 512 a. Consequently, the antenna 512 a may receive signals across an AOA value range 0°≦AOA<180° relative to the plane of incidence 132, where the antenna 512 b may receive signals across an AOA value range 180°≦AOA<360° relative to the plane of incidence 132.

In various embodiments of the invention, the signal location process may compute candidate AOA values AOA=α and AOA=−α, by utilizing antennas 512 a and 512 b in a manner substantially similar to the manner in which antennas 112 a and 112 b were utilized as shown for the system in FIG. 4A. The signal power comparison process may enable computation of signal power level for the signals received via antennas 512 a and 512 b. By comparing the signal power levels for the signals received via the antennas 512 a and 512 b, the AP 102 may determine an antenna indication value, ant_ind_(i)=0, for example. Based on an indication from the signal power comparison process a candidate AOA value, AOA=α, may be selected. In response, an antenna may be adaptively steered to point in the direction AOA=α to enable reception of subsequent signals.

While the exemplary systems shown in FIGS. 1, 4A, 4B and 5 show an AP 102, which utilizes two (2) antennas during a signal location process, various embodiments of the invention may not be so limited. For example, in various embodiments of the invention, the AP 102 may utilize three (3) antennas to practice a signal location process, which determines AOA values in a three (3) dimensional space. Also in various embodiment of the invention the antenna elements of the smart antenna system may be used in place of the separate omnidirectional antennas.

FIG. 6 is a flowchart illustrating exemplary steps for WLAN phase shifter for smart beam steering utilizing omnidirectional antennas, in accordance with an embodiment of the invention. Referring to FIG. 6, in step 602, the AP 102 selects a first antenna among a plurality of antennas, for example a reference antenna 112 a may be selected from the plurality of antennas 112 a and 112 b. In step 603 the AP 102 waits for detection of the signal transmitted by the STA 104. In step 604, the first antenna may be utilized to receive a plurality of preamble symbols. The preamble symbols may be received at the AP 102 based on signals transmitted by the STA 104. Each transmitted signal may comprise a symbol from a PPDU 300. The received preamble symbols may comprise short training symbols.

In step 608, the AP 102 may select the second receiving antenna for example antenna 112 b. In step 610, the second receiving antenna may be utilized to receive a plurality of preamble symbols. In step 616, a phase difference value, θ, may be determined between signals received at the first and second receiving antennas. In an exemplary embodiment of the invention, the phase difference value may be computed as shown in equation [15]. In step 618, the phase difference value θ may be rounded to the closest discrete value θ_(i). In step 620, the candidate angle of arrival values (AOA) may be computed for received signals from the STA 104. The AOA values may be determined with reference to a plane of incidence 132 and the location of a smart antenna system 122 located at the AP 102. The candidate AOA values may comprise AOA=α_(i) and AOA=−α_(i). In step 624 the candidate AOA is selected based on ant_ind_(i).

In step 626, the AP 102 may steer smart antenna system 122 based on selected AOA. In step 628, the smart antenna 122 may be utilized to receive PPDU while oriented in the direction of selected AOA. In step 620, the AP 102 may check received PPDU for errors and in step 630 the AP 102 may change the value of ant_ind_(i) if PPDU was not received correctly.

FIG. 7 is a flowchart illustrating exemplary steps for WLAN phase shifter for smart beam steering utilizing directional antennas, in accordance with an embodiment of the invention. Referring to FIG. 7, in step 702, the AP 102 may select a first antenna among a plurality of antennas, for example antenna 112 a. In step 703 the AP 102 waits for detection of the signal transmitted by the STA 104. In step 704, the first antenna may be utilized to receive a plurality of preamble symbols and the AP 102 may compute the signal power levels P₁.

In step 708, the AP 102 may select a second receiving antenna, for example antenna 112 b. In step 710, the second receiving antenna may be utilized to receive a plurality of preamble symbols and the AP 102 may compute the signal power levels P₂.

In step 716, a phase difference value, θ, may be determined between signals received at the first and second receiving antennas. In an exemplary embodiment of the invention, the phase difference value may be computed as shown in equation [15]. In step 718, the phase difference value θ may be rounded to the nearest discrete value θ_(i). In step 720, the candidate angle of arrival values (AOA) may be computed for received signals from the STA 104. The AOA values may be determined with reference to a plane of incidence 132 and the location of a smart antenna system 122 located at the AP 102. The candidate AOA values may comprise AOA=α_(i) and AOA=−α_(i). In step 724 the candidate AOA is selected based on comparison of power values P₁ and P₂.

In step 726, the AP 102 may steer smart antenna system 122 based on selected AOA. In step 728, the smart antenna 122 may be utilized to receive PPDU while oriented in the direction of selected AOA.

Various aspects of a system for a WLAN phase shifter for smart antenna steering may comprise an AP 102 that enables a signal location process and an antenna selection process. The signal location process may comprise iterative selection of each receiving antenna in a plurality of receiving antennas 112 a and 112 b. Each of the receiving antennas may comprise an omnidirectional antenna. The receiving antennas may be selected iteratively, one at a time. The iteratively selected antennas may each enable reception of one or more signals. Each of the received signals may comprise a preamble symbol, for example a short training symbol 302 b. At least one candidate AOA value may be computed based on the received one or more signals for each of the iteratively selected receiving antennas.

The antenna steering process may comprise steering of a smart antenna 122 based on the plurality of candidate AOA values computed during the signal location process. Subsequent signals may be received via the antenna 122 steered in the direction of the selected AOA. The subsequent signals may comprise one or more data symbols 314 a . . . 314 n.

Other aspects of a system for a WLAN phase shifter for smart antenna steering may comprise an AP 102 that enables a signal location process, a signal power comparison process and an antenna selection process. The signal location process may comprise iterative selection of each receiving antenna in a plurality of receiving antennas 112 a and 112 b. Each of the receiving antennas may comprise a directional antenna. The receiving antennas may be selected iteratively, one at a time. The iteratively selected antennas may each enable reception of one or more signals. Each of the received signals may comprise a preamble symbol, for example a short training symbol 302 b. At least one candidate AOA value may be computed based on a reference signal and on the received one or more signals for each of the iteratively selected receiving antennas. The signal power comparison process may comprise computation of a signal power level for the received signal(s) for each of the iteratively selected receiving antennas. The antenna steering process may comprise selection of beam direction in a smart antenna system based on the plurality of signal power levels computed during the signal power comparison process. Subsequent signals may be received via smart antenna steered in the direction of the selected candidate AOA value.

Accordingly, the present invention may be realized in hardware, software, or a combination of hardware and software. The present invention may be realized in a centralized fashion in at least one computer system, or in a distributed fashion where different elements are spread across several interconnected computer systems. Any kind of computer system or other apparatus adapted for carrying out the methods described herein is suited. A typical combination of hardware and software may be a general-purpose computer system with a computer program that, when being loaded and executed, controls the computer system such that it carries out the methods described herein.

The present invention may also be embedded in a computer program product, which comprises all the features enabling the implementation of the methods described herein, and which when loaded in a computer system is able to carry out these methods. Computer program in the present context means any expression, in any language, code or notation, of a set of instructions intended to cause a system having an information processing capability to perform a particular function either directly or after either or both of the following: a) conversion to another language, code or notation; b) reproduction in a different material form.

Another embodiment of the invention may provide a machine-readable storage having stored thereon, a computer program having at least one code section executable by a machine, thereby causing the machine to perform steps as described herein for a WLAN phase shifter for smart antenna beam steering.

While the present invention has been described with reference to certain embodiments, it will be understood by those skilled in the art that various changes may be made and equivalents may be substituted without departing from the scope of the present invention. In addition, many modifications may be made to adapt a particular situation or material to the teachings of the present invention without departing from its scope. Therefore, it is intended that the present invention not be limited to the particular embodiment disclosed, but that the present invention will include all embodiments falling within the scope of the appended claims. 

1. A method for processing signals in a communication system, the method comprising: performing a signal location process comprising: iteratively selecting receiving antennas in a plurality of receiving antennas one at a time; and receiving at least one signal via each of said iteratively selected receiving antenna; adaptively orienting one or more antenna based on said plurality of signals received during said signal location process; and receiving subsequent signals via said adaptively oriented one or more antenna.
 2. The method according to claim 1, comprising computing a plurality of candidate angle of arrival values based on said plurality of signals received during said signal location process.
 3. The method according to claim 2, comprising adaptively orienting said one or more antenna based on said computed plurality of candidate angle of arrival values.
 4. The method according to claim 2, comprising iteratively selecting each of said plurality of candidate angle of arrival values one at a time.
 5. The method according to claim 4, comprising adaptively orienting said one or more antenna based on said iteratively selected each of said plurality of candidate angle of arrival values.
 6. The method according to claim 5, comprising computing a signal power level for one or more signals received via said one or more antenna when oriented in a direction corresponding to said iteratively selected each of said plurality of candidate angle of arrival values.
 7. The method according to claim 6, comprising adaptively orienting said one or more antenna to receive said subsequent signals based on said computed plurality of signal power levels.
 8. The method according to claim 1, comprising selecting a reference antenna among said plurality of receiving antennas.
 9. The method according to claim 8, comprising computing a correlation value based on said at least one signal received via said reference antenna and said at least one signal received via said each of said iteratively selected receiving antenna.
 10. The method according to claim 9, comprising determining a phase difference value based on said correlation value for said each of said iteratively selected receiving antenna.
 11. The method according to claim 10, comprising determining at least one candidate angle of arrival for said each of said iteratively selected receiving antenna based on said phase difference value determined for said each of said iteratively selected receiving antenna.
 12. The method according to claim 1, comprising computing a signal power level for said received at least one signal during said signal location process for said each of said iteratively selected receiving antenna.
 13. A system for processing signals in a communication system, the system comprising: one or more circuits that enable performance of a signal location process comprising: iterative selection of receiving antenna in a plurality of receiving antennas one at a time; and reception of at least one signal via each of said iteratively selected receiving antenna; said one or more circuits enable adaptive orientation of one or more antenna based on said plurality of signals received during said signal location process; and said one or more circuits enable reception of subsequent signals via said adaptively oriented one or more antenna.
 14. The system according to claim 13, wherein said one or more circuits enable computation of a plurality of candidate angle of arrival values based on said plurality of signals received during said signal location process.
 15. The system according to claim 14, wherein said one or more circuits enable adaptive orientation of one or more antenna based on said computed plurality of candidate angle of arrival values.
 16. The system according to claim 14, wherein said one or more circuits enable iterative selection of each of said plurality of candidate angle of arrival values one at a time.
 17. The system according to claim 16, wherein said one or more circuits enable adaptive orientation of said one or more antenna based on said iteratively selected each of said plurality of candidate angle of arrival values.
 18. The system according to claim 17, wherein said one or more circuits enable computation of a signal power level for one or more signals received via said one or more antenna when oriented in a direction corresponding to said iteratively selected each of said plurality of angle of arrival values.
 19. The system according to claim 18, wherein said one or more circuits enable adaptive orientation of said one or more antenna to receive said subsequent signals based on said computed plurality of signal power levels.
 20. The system according to claim 13, wherein said one or more circuits enable selection of a reference antenna among said plurality of receiving antennas.
 21. The system according to claim 20, wherein said one or more circuits enable computation of a correlation value based on said at least one signal received via said reference antenna and said at least one signal received via said each of said iteratively selected receiving antenna.
 22. The system according to claim 21, wherein said one or more circuits enable determination of a phase difference value based on said correlation value for said each of said iteratively selected receiving antenna.
 23. The system according to claim 22, wherein said one or more circuits enable determination of at least one candidate angle of arrival for said each of said iteratively selected receiving antenna based on said phase difference value determined for said each of said iteratively selected receiving antenna.
 24. The system according to claim 13, wherein said one or more circuits enable computation of a signal power level for said received at least one signal during said signal location process for said each of said iteratively selected receiving antenna.
 25. The system according to claim 24, wherein said one or more circuits enable adaptive orientation of said one or more antenna based on said plurality of computed signal power levels. 